Wave analyzer



Dec. 26, 1950 Filed Jan. 27, 1943 INPUT 3 v.00 CYCLE INPUT SA'TOOTH OSCILLATOR POSITIVE SAVITOOTH G. W. COOK WAVE ANALYZER 3O SQUARE PARALLEL GlANNfl-S WITH BAND-PASS FILTERS TRIFPING PULSE N ELECTRONIC "ITO" sec.

6 FREQUENCY CONPENSATING PULSES 9 Sheets-Sheet 1 3O EXPONENTIAL PU LSES OUIPUI CIRCUIT um: PULSE8\ SIGNAL #aeousncv Ann was i common.

l 1:00 Trams muss STAI RWAVE OSCILLATOR NEGATIVE STAIRWAVE FIG. 1

GATHODE RAY OSOILLOORAPH P08 ITIVE STA! R'AVE so an" I" a an OUIPUI ll loox INVENIUR. GEORGE W. COOK Dec. 26, 1950 cs. w. cooK 2,535,043

WAVE ANALYZER Filed Jan. 27, 1943 9 Sheets-Sheet 2 I 1 Ill IxzxIIz: lllllll 4o III POSITION CALI DUMMY MARKER f'llllllll-lllllIIIIII|||||| [FF-Dumnvmaxn was. 25 50 FOR ZERO REFERENCE I00 200 400 e00 :600 3200 6400 |o,ooo'-"' CYCLES PER SECOND FIG. 2-

9 so I 0 4.0V I II.- .I II.-

mmvmn GEORGE w. 000K G. W. COOK WAVE ANALYZER Dec. 26, 1950 9 Sheets-Sheet 3 Filed Jan. 27, 1943 IOOK T U P WW 0 G E I INPUT All '1'" 2 MEG.

in" J MEG.

FIG. 5

OUTPUT FIG. 6

INVENTOR.

GEORGE W. COOK Dec. 26, 1950 s. w. cooK 2,535,043

WAVE ANALYZER Filed Jan. 27, 1943 9 Sheets-Sheet 4 OUTPUT VOLTAGE IN PUT VOLTAGE FIG. 7

OUTPUT VOLTAGE IN PUT VOLTAGE I I0 I00 |,0OO 10,000 100,000

rnsousucv Fl 6. a

INVENTOR.

GEORGE W. COOK 26, 1950 a. w. COOK 2,535,043

IAVE ANALYZER Filed Jan. 27, 1943 9 Sheets-Sheet 6 INPUT FROM MASTER OSCILLATOR INPUT FROM SWITCH OUTPUT TO & O OATNOD! MY TUIE 3' i an:

FIG. 10

. T mavim. FIG. 13- GEORGE w. 000K G. W. COOK WAVE ANALYZER Dec. 26, 1950 9 Sheets-Sheet 7 Filed Jan. 27, 1943 roam OsooT 02- :PCIn 30am Iota o Una-at 052:.

l y u 1 0 so: 0 s03 p535 .25. 595, 2. 0:95am

INVENTOR.

GEORGE W. COOK G. W. COOK WAVE ANALYZER Dec. 26, 1950 9 Sheets-Sheet 8 Filed Jan. 27, 1943 to. m

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waw mum GEORGE W. COOK Dec. 26, 1950 a: w. cooK' 2,535,043

' WAVE ANALYZER Filed Jan. 27, 1943 9 Sheets-Sheet 9 C Y ii 0 a gr 0 FIG. 14

INVENTOIL GEORGE W. COOK Patented Dec. 26, 1950 wnvn ANALYZER George w. Cook, Washington, D. 0.

Application January 27, 1943, Serial No. 473,711

19 Claims. (Cl. 250-27) (Granted under the act oi March 3, 1883; amended-April 30, 1928; 370 0. G. 757) This invention is in wave analyzers; As herein described and shown, it is intended to operate in substantially the audio frequencies only, but it will be obvious that in principle it is not thus limited.

In operation, it rapidly resolves and indicates the intensities of sounds simultaneously in a series oiiselected'irequencies originating in a complex sound source. More accurately, its readings, which are proportional to acoustical pressure, must be squared ii quantities indicating intensity strictly are desired.

The 'difllculties involved in mathematical and mechanical analyses oi complex wave forms have stimulated the development oi electronic analyzers.- The prior art devices, generally speaking. are of two types. I

One type involves the use oi a single highly selective band-pass filter. A voltage corresponding to.the wave iorm oi the sound being studied is heterodyned-with a search tone and applied to'the'illter. An analysisis obtainedas the search tone varies in frequency. This type oi analyzer is well known and widely used; but is subject to limitations in speed oi analysisand resolving power. One common type requires about ninety seconds to complete an analysis extending continuously through the audible region. It is evident that this type oi analyzer is useful only with prolonged, unchanging sounds.

Inthe' second p a plurality oi filters are arranged in parallel, and the output oi each ill- I ter. is indicated by the height oi a corresponding line on the screen oi a cathode-ray oscillograph.

Connection in turn between each illter and the cathode-ray tube is, accomplished up to about ten times a second by a mechanical switch.

The present invention is broadly oi the second oi. the'abcve types oi instruments. No mechanical switch is used, but by means oi a novel electronicswitching circuit, the switching rate is increased irom about ten to sixty cycles per second. It is to be understood, however, that the novelty oi this invention is not limited to the electronic lwitch, nor to the substitution thereof ior a mechanical switch. Neither is the speed of the electronic switch herein illustrated limited to a speed oi sixty cycles per second.

This invention isadapted to receive an electric potential, corresponding to the sound under z investigation, and apply it to a parallel arrange ment of twenty-eight separate filter channels, comprising an all-pass, a low-pass, a high-pass and twenty-five band-pass filters. The bandpass fllters are spaced at intervals of one-third octave throughout the audio range from twentyflve to ten thousand cycles per second. The output signals oi the filter channels are "scanned by the electronic switch sixty times per second, and the composite output of the electronic switch is observed as the vertical defiectionon a cathoderay oscillOElsph.

The analyzer also provides a. horizontal deflection voltage for the cathode-ray oscillograph, so as to put on the screen a plot of the distribution of the sound intensity as a function of frequency.

One object oi the invention is the provision oi a wave analyzer which will substantially instantaneously resolve into pro-selected components a complex wave, and substantially simultaneously produce for visual or photographic inspection the values oi-all oi the components.

Another object isto provide an electronic switching means which will apply to a single line successively and repeatedh; and with great rapidity the outputs oi a plurality oi circuits.

A iurther object is to provide a stairwave or stepwave generator and means ior counting the steps oi the generator and resetting the circuit aiter a'predetermined number oi steps have been completed.

It is also an object of the invention to use a so-called ring circuit oi gas-tilled triodes, and to provide means for inhibiting the'flring oi more than one such tube at a time.

A' still iurther object is the provision of means by which two associated ring circuits may be started and maintained in periect predetermined time-phase with each other.

It is also an object oi the invention to provide with a circuit the output oi which is normally a wave iorm with undesirable voltage peaks means for eliminating the said voltage peaks.

Another object oi the invention is the provision oi a simple and eiiective electronic voltage regulator.

Additional objects oi the invention will be apparent irom a reading oi the iollowing specifications and claims.

In the drawings:

Figure 1 is a block diagram of the analyzer of my invention. The approximate wave forms are indicated beside the pertinent leads.

Figure 2 is a typical pattern such as appears on the screen of the cathode-ray tube.

Figure 3 is a circuit diagram of a typical bandpass filter channel.

Figure 4 is a circuit diagram of the low-pass channel.

Figure 5 is a circuit diagram of the high-pass channel.

Figure 6 is a circuit diagram of the all-pass channel.

Figure '7 shows the response curves of the lowpass, the twenty-five band-pass, and the high pass filter channels. H

Figure 8 shows the response curve of the allpass channel.

Figure 9 is a diagram of the switchingcircuits.

Figure 10 is a diagram of the output circuit.

Figure 11 illustrates the timing circuits.

Figure 12 is a diagram of the filter power supply circuit.

Figure 13 is a diagram of the main power sup- Figure 14 illustrates one form of the electronic voltage regulator of my invention.

Figure 15 shows a modification of the voltage regulator of Figure 14.

GENERAL DESCRIPTION With reference to the block diagram of Figure i, it is the function of the acoustic analyzer of this invention to receive a signal of complex wave form. to resolve this signal int'ocomponents falling within definite frequency bands, and to indicate the relative values of these components. The quantity with which the instrument deals is voltage per unit frequency interval, integrated over the respective frequency bands and averaged in some fashion over time.

This is accomplished in the followin manner: a

A signal obtained trim a microphone or other source is applied 'simu.aneousi'y to a parallel arrangement of twenty-eight filter channels. Of these channels, twenty-'nv'e contain band-pass filters corresponding to the desired components. one contains a low pass filter, and one. a highpass filter the latter two cover components well below twenty-five and well above ten thousand cycles per second. The remaining channel has an essentially fiat frequency characteristic for picking up and averaging sounds over the whole useful range of the analyzer.

Each channel contains an amplifier and a signal rectifier. These. as well as some other elements mentioned in the general description do not appear in the block diagram of Figure las elements, They will be found in subsequent figures and will be described in connection therewith. The output of the rectifier is applied to a condenser and shunt resistance having a time constant of approximately Q3 second. The voltage appearing across the condenser is proportional to the vector sum of the voltage amplitudes of the componentsof the input signal lying within the frequency limits of the associated channel, and this voltage determines the output signal of each filter channel.

By means of a novel switch the output of each of the twenty-eight channels is successively aplied sixt times per secohd too common line. There are thirty steps in the switch, so that each channel is connected for an interval of /isoo secarated by intervals of constant voltage.

4 ond. The two extra steps (there bein but twenty-eight channels) are required for synchronization and are normally blank. The con. mon output line leads through another networx to the vertical deflecting plates of a cathode-ray tube. The switch is also used to count the steps of a stairwave (also known as stepwave") generator and to reset this circuit after thirty steps have been completed. The timing of the switch is controlled by a master point pulse oscillator.

Them-axis deflection signal-'applled to the horizontal eehecnh platbs of the dsiudgm h consists of thirty successive increases of voltage, sep- This sweep signal is obtained from the stairwave generator. which is controlled by the master oscillater and by the electronic switch. Another signal from the stairwave generator i combined with a sawtooth sig'nal synchronized to the power line frequency and this combination is used to control the frequency of the master oscillator so that it is exactly thirty times the line frequency. A 8lgnal from the master oscillator also controls the output circuit and synchronizes it with the switching circuits.

The composite output of the electronic switch is applied to an output circuit before passing to the vertical deflecting plates of the oscillograph. This output circuit modulates the output signal of the electronic switch and controls the final indication on the cathode-ray oscillosraph. The timing signal applied to the horizontal deflecting plates of the oscillograph is reproduced on the screen as a series of thirty equally spaced spots, corresponding to the thirty steps of the stairwave. If the output of the switch were applied directly in the vertical deflecting plates of the oscillograph, the screen pattern would consist of thirty spots appearing at various heights above the spots on the axis, The height of the displaced spot in each case would be proportional to the output voltage of the corresponding channel. The output circuit transforms thisthirtystep histogram output of the electronic switch into thirty exponential pulses as shown in Figure 1, extreme upper right hand corner. The'height or each exponential pulse is proportional to the signal amplitude of the corresponding channel in the switch output. The pattern on the oscillograph screen then assumes the appearance of a set of thirty vertical lines or thermometers" which rise and fall as the output voltages of the corresponding channels change.

Merely because of lack of space, the oscillograph pattern of Figure 1 does not include the full number of "thermometers." For the same reason the stairweve form shown does not include thirty steps.

A typical pattern appears in Figure 2, wherein will be seen two horizontal scales below the pattern proper. The upper scale 40 is graduated from i to 30, and each marker on the scale represents one of the filter channels, except for the markers at i and at 30. which latter are so-called "dummy" markers, the pattern spots above these indicating the base line above which the heights of the other lines are measured. From a comparison of upper scale 40 with the lower scale ll (which is similar but is calibrated in cycles per second), it will be seen that marker 2 of scale 40 represents the low-pass filter values; markers 3 through 21, the band-pass channel responses; It. the high-pass; and 29. the all-pass. The thermometer" above marker 29, in other words, the all-pass indication, has a diilerent vertical scale than the others of the pattern, since otherwise it commonly would 'be iofl the screen entirely. The arrangement that makes this possible will the described :later in the specification.

.It :should the-understood that Figure 2 is somewhat "diagrammatic. In the oscillographic pattern itself, the'background, of course, is dark and the thermometers" appear as streaks oflight. Further, the thermometers are not quite as regular in .form as they appear in thedrawing.

A standard commercial cathode-ray oscillograph is used to indicate .the amplitudes of the output voltages of the various channels. Minor modifications of thecommercial form of the oscillograph circuit are necessary to adapt it to the type of indication desired in this instrument, but these will be obvious to those skilled in the art.

The analyzer is designed tooperate on lilo-volt -60 cycle regulated power. A standard voltageregulating transformer canibe used to supply this :power :from' a single phase 220-vo1t- 60-cycle .line. .Two :power supplies, each containing electronic voltage regulators, provide plate voltage to the nlter'channels and to the :timing circuits, switching circuits, and output circuits respectively.

DETAILED DESCRIPTION As is apparent from an inspection of the drawlugs and of the brief descriptions thereof, each figure represents a different circuit component of the invention. Due to the number and complexity of these circuits, it is notpossible to show in detail in one figure the whole combination; instead, thedescription and the block diagram must escapes the character t"; if the numerical value is followed by "a the-quantity is micro-microfarads. Values of inductances are in henries. These values, when important, are given, either in the specification or on the drawings. If the latter, the values appear, when space permits, immediately adjacent the elements in question or the reference characters pertinent thereto. Where this practice would congest a portion of a drawing unduly, the value may be spaced from the element to which it applies and connected therewith by a dotted line. If a component is re peated ina circuit, the value thereof is given only once.

FILTER CHANNEL CIRCUITS As previously described, twenty-eight filter channels are arranged in parallel'lbetween-theinput receptacle and the input to the electronic switch. Twenty-five of these channels contain band-pass filters which have tuned frequencies diflering successively -by one-third of van octave. One channel contains a low-pass-filter having-5a cut-oil at about twenty-five cycles persecond; one contains a high-pass filter having .a cut-off at about ten thousand cycles per second; and one contains an amplifier having a response uniform within plus or minus five per cent from about two cycles to thirty thousand cycles-persecond.

Table A gives th filter components for the par.- ticular embodiment of the invention which is herein described. It will be ovbious thatmodiflcations of the system, as, for instance, the use of different frequency bands, :willrequire changes in the characteristics of the-filter elements.

Table A Component Number in Figure 3 60, 07 68 09, -71,-72 Fmquem 01 56 46 02, 63 M 65 cies, Unit Value K K K n l n1. #1. #1. h.

I -0-25 See Figure l.

100 40 8 w 100 0. 0500 0. 300 0. 0600 40 0. 1 0. 10 0. 25 (1)300. 40 8 100 000 0. 0500 0. 240 0. 0380 40 0. 1 0.10 0. 25 5 940 169 40 4 a 100 0. 0500 0.240 0.0380 20 0.1 0.10 0.10 3.740 200 40 10 100 0. 0100 0. 0. 0300 u 0. 1 0.01 -0. 10 3.;150 252 40 8 40 (X10 0. 0100 0. 180 0.0300 8 -0. 1 -0. 01 0. 10 2 m 40 10 100 M0 0. 0100 0.120 0. 0190 8 0. 1 0. 01 0. 10 2.130 400 40 0.07 n 30 0.0100 0.120 0.0190 8 0. 1 0 01 0. 10 1.-344 504 250 0 23. 1 260 0. 0010 0. 120 0. 0106 8 0.1 0. 01 0. 01 0. 846 085 260 9 I 30 0. 0010 0. 000 0. 0090 8 0.1 0. 01 0. 01 1.005 800 250 b 28.3 000 011110 0.000 0.0090 .8 0.1 0.01 0. 01 0. 672 was 260 2. 80 40 7. 6 0. 0010 0. 000 0. 0096 8 0.1 0. 01 0. 01 0. 423 1770 500 8 260 50 0. 0002 0. 036 0. 0058 8 0v 1 0. 01 0. 01 0. 390 10(1) 500 8 0 71.4 0.0(02 0.021 0.0088 8 0. l 0.01 0.01 1 0.009 1116 600 4. 70 a 60 0. (X102 0. 024 0.-(X)38 8 0. 1 0. 01 0. 01 0. 232 2540 500 2. 00 I!) 32. 0 0. W02 0. 024 0. 0038 8 0. 1 0. 01 0.01 0. 146 3110 500 0. 07 500 100 50w: 0. 012 0. 0019 8 0. l 0. 01 0. 01 0. 184 4032 600 ii a 50 50pm 0.012 0. (X119 8 i 0.1 0.01 0 01 0.116 woo 600 4 0 60 50 m 0. 012 0. 0019 8 0. 1 0. 01 0. 01 0.0732 0400 600 4. 44 w 1500 60m: 0. 006 900 8 0. 1 0. 01 0.01 0. 002 8001 we 8. 33 we 100 50w; 0. 000 000 8 0. 2 0. 01 0. 01 0.058 10 See Figureb 0-- Sec Fligure 0 The values oi resistor! corresponding to resistor 73 of Figure 3 must be carefully selected to give 'ilie filter channels the desired charaoueriltim. The Vllllill are not listed because the selection requi.-.. closer tolerances than those usually implied by the nominal value of a roeuitcncc.

l in this table, as in the drawings. a capacity value, whenfcllowed by the notation "ml" is in terms of micro-microiamds.

be relied upon to explain the relationships between the parts.

Resistance values where given are in ohms (O), kilo'hms (K) or megohms (meg). Capacitances Consider first the typical band-pass channel of Figure 3. The arrangement of resistance 45 and condenser '46 provides a preliminary filtering action. The signal is then amplified by penare in microfarads, when the value is followed by 7 5 tode tube 41 and fed into the filter network,

The output of the filter network is fed through a gain control 48 to the grid of a second amplifier tube 49 and thence to the grid of tube 50. The latter tube uses both plate and cathode coupling to apply a push-pull signal to the plates of a fullwave rectifier The rectified output voltage appears across resistance 52, condenser 53 and resistance 54. This network has a time constant of 0.2 second (for discharge), and, accordingly, rapid variations of the signal are partially filtered out. A fraction of the voltage across resistance 54 is applied to the grid of the direct-coupled, cathode-follower tube 55. The output of the cathode network of this and every other channel is connected to the suppressor grid of a separate matrix tube of the electronic switch (Figure 9), to be later described.

In each filter channel there are four resistance controls. Th first, 56, determines the selectivity of the filter and is permanently set in accordance with the values given in Table A. Potentiometer 48 also is not normally varied. It is adjusted so that a desired input level to the filters. between 0.1 and 1 volt root-mean-square, yields a voltage at the plates 01 5| suitably within the linear range of this type of tube. Potentiometer 54 is the Gain Zero adjustment which will be further mentioned later. It controls the signal reaching the grid of tube 55 and ultimately the amplitude observed on the oscillograph screen. The usual adjustment is such that 1 volt R. M. S. (root-mean-square) into each channel produces a 2-inch deflection. Potentiometer 51, the "Balance" adjustment, determines the potential of the suppressor grid of the associated matrix tube in the electronic switch. It and the corresponding Potentiometers of the other filter circuits are adjusted so that, with no signal, equal displacements, about 0.2 inch for all channels, are observed on the screen. The output signal of a channel is the variation above this initial voltage, and the matrix tube suppressor grid accordingly serves also as a signal grid.

The low-pass, high-pass and all-pass filter channel circuits are shown in Figures 4, 5, and 6, respectively. The high-pass and low-pass channels differ from the band-pass channels only in the filter design; The all-pass channel contains only the last four tubes of a typical channel, These filter channels are fundamentally similar to that of Figure 3, and will not be described in detail. The values of the important components appear on the drawings.

The frequency curves of the filter channels appear in Figure '7. Figure 8 is a separate curve of the all-pass channel response.

SWITCHING CIRCUITS The purpose of the switching circuits is to apply voltage levels proportional to the output voltage levels of the twenty-eight channels to a single line successively and repeatedly. The switching circuits consist of the following fundamental circuits: The fast-switching ring, the inter-ring pulse-generator, the slow-switching ring, the clipping tubes, and the matrix tubes.

The following description rei'ers chiefly to the circuit diagram of the switching circuits in Figure 9. Reference characters and electrical values therefor are given for only a portion of each circuit. Unless otherwise noted, the components and the values thereof are repeated throughout the respective circuits. Tubes in the fast ring are numbered from 80 to 85, inclusive. Tubes in the slow ring are numbered I00 to I04, inclusive.

8 Fast switching ring Positively-polarized point-pulses, i. e., sharp pulses of voltage which last for only a small fraction of their period of repetition, are delivered from the master pulse oscillator through the condenser |05 at a repetition rate of 1800 per second. These pulses are applied to the grids of all six tubes of the ring through individual blocking condensers, as I08. The six tubes of the ring are thyratrons (gas-filled triodes) which have such a high negative grid bias that under normal conditions they are non-conducting. Under equilib rium conditions, the positive input pulses are not of sufilcient magnitude to fire the tubes.

Consider the situation when one tube is already conducting, say 8|. Current flowing through this tube raises the potential of the cathode because of the IR. drop in resistor |0'|. By 11?. drop" is meant the voltage drop in the resistance due to the passage of current there through. Current flows from the cathode of tube 8| through resistors I08 and I08. The IR drop in resistor I08 reduces the grid bias of tube 82, but not sufflciently, however, to fire 82. The decreased bias voltage is such that the next positive pulse from the master pulse oscillator, ,5 second later, will cause 82 to fire. Thus, current through tube 8| primes tube 82, so that th next pulse fires 82 in preference to all other tubes in the ring. While tube 8| is conducting, th condenser ||0 is positively charged on the right hand side and at ground potential on the left hand side. When tube 82 becomes conducting, the left hand plate of this condenser is suddenly raised to a positive voltage well above ground. This drives the cathode of tube 8| momentarily positive with respect to its plate until the induced charge on I I0 leaks ofl. through resistor I01. Conduction in thyratron 8| ceases since its plate is negative with respect to its cathode, On the next pulse, the cycle is repeated with tubes 83 and 82.

Each tube as it becomes conducting extinguishes the preceding tube and primes the next tube. The tube 85 acts on tube in the same ltnanner as any other tube acts on its succeeding ube.

On the basis of the description to this point there could conceivably be established a condition with alternate tubes in the ring conducting simultaneously. That is, 80, 82, and 84 might fire together and prime 8|, 83, and 85 for firing on the next pulse from the master oscillator. When the latter fired, they would first extinguish, then prime, 80, 82, and 84. The cycle would be repeated indefinitely at a rate of 900 per second. Such behavior is inherent in thyratron counting rings with more than four elements. In this switch such a tendency is inhibited in a novel manner by the capacitative coupling 5 between the cathodes of tubes 82 and 84. When 82 ignites, an extinguishing pulse is delivered to 8| and 88. In addition, the cathode of 84 is made positive momentarily and this pulse is delivered to the cathodes of 85 and 83 through condensers H8 and Ill, respectively. Thus, if the ring starts out with more than one tube conducting, all tubes except 82 will be extinguished after one cycle of operation of the ring.

The method of self-quenching exhibited by this ring circuit prevents the accidental condition in which two tubes are fired simultaneously from continuing for more than one cycle of operation of the ring, which in this case, is laoo second. In actual practice. the operation i so fast that the ring assumes stable operation after the first two or three seconds of starting time, and the quenching oi multiple firing is so fast that it is never observed. I

The ring is started by unusually large pulses delivered from the master oscillator Just after the power is turned on. The first pulse has sufficient magnitude to fire one or more of the six tubes. If more than one tube fires as a result of these enhanced pulses, the extra tubes will be extinguished after one cycle of operation of the ring, as previously described.

Inter-ring pulse generator The input for the inter-ring pulse generator is obtained from the cathode of tube 80. When 80 is ignited, 85 is extinguished. The cathode of tube 80 goes highly positive momentarily, then rema'ns at a lower but fixed positive value during the time the tube conducts. The resulting peaked square-wave signal is applied to the grid of thyratron I20 through resistors I2I and I22. I20 is normally non-conducting, but ignites on the peak of the positive signal from the cathode of tube 80. I20, therefore, fires with the same frequency as namely. 300 times per second. A condenser, I23, is in parallel with the tube I20. This condenser charges through the resistance I24. The voltage to which it charges is limited by a diode, I25, which in turn determines the amplitude of the pulse developed across resistor I26. Extinction of tube I occurs while tube 80 is still conducting.

Positive point-pulses are thus obtained from the tap on I26. They have a duration of a few microseconds and a frequency of 300 per second.

Slow-switchingring The input to the second or slow switching ring consists of the positively-polarized pulses, having a frequency of 300 per second, which are generated by tube I20. These are applied to the grids of all five thyratrons (100 to 104, inclusive) in the slow ring through individual condensers, as I21. The tubes are normally nonconducting, and the positive pulses applied to the grids are just great enough to cause any of the tubes to fire. When a given tube is conducting it raises thegrid voltage of the succeeding tube by means of the connection between the cathode of one tube and the grid of the following tube, 1. e., resistor I28. Thus. if tube IOI is conducting, the grid bias of I02 is reduced to such a" point that the next pulse applied to the common. input will ignite tube I02 a few microseconds before it has increased sufficiently to reach the ionization potential of the other tubes. When I02 is fired, a pulse appears on the cathodes of IM and I03, through the intercathode condensers I29 and I30, respectively. Tube IN is consequently extinguished, and tube I08'is prevented from firing. In addition, a; positive pulse is delivered to the cathode of I04 through condenser I-3 I-. This prevents tube I04 from firing and makes-the cathodes'of I03 and I00-more positive than they would otherwise be. Thus, although the pulse delivered to the common grid input has sufiicient magnitude to fire any of the five tubes, the tube which is primed actually fires before the other tubes, and conduction of this tube prevents the other tubes of the' ring from firing.

The priming on tube I00 is obtained partly from tube I04 and--partly from tube ilil. Resistor I32, between the cathode of tube' I 04- and the,

grid of I00 is larger than the analogous resistors. for example, I20. It is shown as 300K instead of 100K. There is also a lead from the cathode of tube 00 of the fast ring to the grid of thyratron I00 through resistor I30. The firing of tube I04 alone does not fully prime tube I00; the latter will be fully primed when tubes I04 and fire together.

This novel double priming of tube I00 contributes what may be called a selective starting" feature to the slow ring for, by this means, the first tube of the slow ring is forced tofire when the first tube of the fast ring fires; this insures perfect time-phasing ofthe two rings. If, by chance, the firing sequence of the slow ring becomes disorganized; the tube I04 will remain fired and will provide half-priming on tube I00 until the time when tube 00 is fired. Ignition of this tube produces full priming of tube I00 and starts the ring operating again in proper sequence and time-phase with respect to' the fast ring. It is because of this positive "lock-in between the tworings that asynchronizing signal can be taken from the slow ring to' the stairwave generator, and ultii'nately', tothe master oscillator, to keep the entire system in proper sequence and time-phase and in synchronism withthe GO-cycle power line.

The selective starting andthe waiting until synchronism" features of the slow ring, which are provided by the two sources of. priming for tube I00 and which permit-the perfectsynchron sm of the two rings. are not essential, because of the positive extinction of other tubes by condensers Iii, I2S,-etc. 'They are important,-however, adding to the stability ofoperation of the slow ring and-the combined-rings.

When tube L00 ignites, the voltage of the cathode becomes-positive A- lead istaken from this cathode-to'the stair-wavegenerator. The signal on this lead consists of a positive voltage during the time N10 is conduct ng. I00 conducts for an interval of /:mu aecond'with afrequency of- 60 per'second- This si nal iscarried to the stairwave generator ofthe timing circuits (Figure 119*. The acton of this p lse will bedescribed later-in the section ontheTiming-Circults. Thus the switching ringaact-not-onl-v as control tubes for the matrix tubes of the switch, but also as a counting circuit. Th s has the efiect of stabilizing and synchronizing the stairwave form watpattern of exactly thirty steps.-

Clippingt'ubes The term clppingtube" is usedherein to-denote a tube the function of which is to clip oflundesired peaksof a given voltage wave, i. a, theclipping tube operatesas avoltage limiter. In its application-here, the cl pper is used to cut offthe sharp peaks caused by the extinguishing action ot the cathode coupling condensers; these peaks, in both a positive and a negative direction, are of about twce the magnitude of the switching potential developed at the cathode of the gas triode. Failure to efiminate them causes spurious and undesirable voltage pulses in the output of' the electronic switch which tend to confuse its already-complicated composite out put signal. The appication of this clipping" principle to the elimination of the undesirable switching pulses obta'n'ed from the ring counter types of electronic switch is believed to be novel. One-tube; a duplex diode, is used to limit the output signal from each thyratron' in the two ring circuits. These cli ping. tubes lay-p sharp, high-frequency pulses in the output of the ring tubes and provide a regular square wave. All clipping tubes for the fast ring are connected in the same way; likewise, all clipping tubes for the slow ring are connected in the same way. However, because the maximum output signal voltage of a tube in the fast ring must be negative or zero, while the output voltage of a tube in the slow ring must be positive, the groups of clipping tubes for the two rings are connected differently.

The clipping tubes for the slow-ring thyratrons I to I04, inclusive, are numbered I40 to I44, respectively. Consider as an example the duodiode I42. The output of thyratron I02 consists of a positive square wave with a sharp positive peak on the leading edge of the square wave and a sharp negative peak on the trailing edge. When a negative voltage is applied to the ring side of tube I42, the cathode I42 is ne ative with respect to its plate. The lower diode conducts and the negative signal is effectively short-circuited to ground. This limits the output of thyratron I02 to positive voltages.

The operation of the other part of tube I42 is as follows: When the ring side p ate is more posit ve than its cathode I42", the other diode of I42 (i. e., cathode I42 and its associated plate) conducts. The signal volta e is thus limited by the volta e of the cathode I42 of the tube. This cathode voltage is determined by the equilibrium voltage of condenser I45 shunted by res stance I 46. This voltage is developed by the continuous flow of current from each clipper tube in succession. Condenser I45 is constantly being charged since one of the five slow-ring clipping tubes is always conduct n It discharges at a constant rate through resistance I40. Consequently the maximum va ue of the output signal of the rin tube is determined by the value of resistance I46.

The clipping tubes for the fast rin tubes 80 to 85, inclusive, are numbered I50 to I55, respectively. Now cons der tube I5I. The output of thvratron 8i consists of a positive square wave with positive and negative peaks as before. However, the reference volta e of the positive p lse is to be below cathode potential since the entire s nal is to be a plied to a control rid. Conseouently the upner limit of this signal m st be litt e reater than zero volta e. This is accomp ished as follows: When plate I5I of d plex diode I5I is positive, the ri ht hand diode of th s tube conducts: this efl ctivelv shorts the s nal to gro nd. When cathode IIiI of t be I5I is negative with respect to its late I5I. the left hand diode of the tube conducts. Therefore, the output of tube 8| cannot be more pos tive than the volta e drop in the diode (referred to ground) and cannot be more negative than the plate ISI' of tube I5I. The voltage of this p ate is fixed by the voltaee across condenser I50. This condenser is constantly being char ed because one of the clipping tubes for the fast ring is a ways conducting. It is constantly being discharged throu h the shunt I51. Consequently, the reference voltage for the pulses delivered by thyratron BI is negative and is determined by the resistance I 51.

The networks comprising (for example) resistors I80, I6I, and I02, in the one case. and I10, HI, and I12, in the other, determine the grid bias voltages of the matrix tubes f r the slow ring and the fast ring.

12 Matrix tubes The switch proper consists of thirty pentodes arranged in rows of six tubes each and columns of five. The clipped output of each thyratron in the fast ring is applied to the control grids of all of the five tubes of the corresponding column. The clipped output of each thyratron in the slow ring is applied to the screen-grids of all of the six tubes of the corresponding row. The matrix tubes are normally non-conducting, since both control and screen grids are biased beyond cutoff.

If tube 8| is conducting, however, the control grids of all of the five tubes in the column associated with it are brought above cut-off potential. If thyratron I02 is conducting, the screen grids of all the six tubes in its row are brought above cut-ofl potential. For a matrix tube to be conducting, both the screen grid and the control grid must be at elevated voltages. Consequently, only pentode I15 is conducting.

The cycle of operations is as follows: Assume that thyratron I00 of the slow ring is conducting. The fast ring goes through its cycle with each of the six tubes conducting in the order to 85. When the fast ring completes its cycle, I00 is extinguished, and I 0| becomes conducting. The cycle of the fast ring is repeated, and the conducting tube in the slow ring changes again. This continues until all combinations of pairs between the fast and slow rings have been conducting simultaneously. One complete cycle of the switch occurs every of a second in the ap paratus herein shown and described.

The output lead of each of the twenty-eight filter channels is connected to the suppressor grid of one of twenty-eight of the thirty matrix tubes. The two remaining tubes, as I16 and I11, have fixed voltages applied to their grids to provide a reference level for the output signal .voltages of the other tubes. These two tubes supply the dummy markers on the oscillograph screen. All of the tubes in the switching matrix have a common plate resistor, I18. The output signal of the switch is taken from this common plate lead to the output circuit, and it is fed to the composite output circuit of the analyzer.

OUTPUT CIRCUIT The output circuit, Figure 10, receives a complex signal from the electronic switch and modifies this signal so that a convenient pattern will be obtained on the cathode-ray tube screen. The input to this circuit consists of a histogram in which the voltage at a given time is proportional to the output voltage of the corresponding filter channel. Each of the thirty matrix tubes of the switch circuit is connected to the input line for an interval of hate second at a rate of sixty times per second.

The input signal is applied directly to the grid network, I80 I80 I80 of pentode tube I 80. During each of the periods of /1800 second the grid voltage is constant and the plate current is constant. Consequently, during each period, condenser I 8| is charged. The time constant of this condenser is short compared with lisoo second, so that I8I is practically fully charged after about A of this period. The voltage across IOI is essentially equal to the plate voltage of tube I80, which is determined by the current flowing through th s tube and resistor I82 and is proportional to the signal grid voltage.

Normally thyratron I83 is not conducting. At

aosxgoes 13 the end of each /iaoo second interval, a positive pulse (obtained from the timing circuit) is delivered to the gridof I83. This pulse ignites I83 and condenser I8I discharges.

The voltage across tube I83 drops almost instantaneously to a value which will not support the discharge, and the tube is extinguished. The charging cycle is then repeated. Again the final voltage across condenser I8I is determined by the plate current in tube I80.

The voltage across condenser I8I increases exponentially with time to about 97 per cent of the charging voltage, then decreases abruptly to zero, then increases ex onentially again to about 9? percent ofa different charging voltage, which is determined by the output amplitude of the particular filter channel'which is connected to itthrough the electronic switch. This cycle is repeated indefinitely. This signal is applied to a duplex diode I84. When arranged as shown this tube removes negative peaks introduced into the signal by the action of t-hyratron I83. The series rectifier willnot pass the negative part of the signal. However, due to the inter-electrode capacity of the tube, sharp negative peaks are passed'through the rectifier. These are shortcircuited to ground by the parallel rectifier.

Thediode I85 in the cathode lead of pentode I80 serves two purposes. One is to provide a cathode load and introduce degeneration into the operation of tube I 80; this could equally well be done by aresistor. Further, small slow changes in the-heater voltage of the matrix tubes of the switch, due to supply-line voltage changes, produce corresponding level changes in the voltage of the output signal. Diode I85 has the same heater characteristics as the tubes of the switching matrix. When current through the switch is increased by increased heater voltage, the grid of tube I80 becomes more negative and this tube becomes less conducting. However, there is an increase in conductivity in tube I85 due to the same change in heater voltage which decreases the bias on both control and screen grids of I80, thus compensating for the change as it occurs.-

Ihe purpose of triode I86 is to operate as an impedance transformer by means of cathode loading and thus to provide a lower impedance output'line to the vertical deflecting plates of the oscillograph. This output tube also isolates the sensitivitycontrol I81 from the effects of varying external loading conditions.

The adjustable resistor I80 has an important function not yet described. Itprovides what may be't'erm'e'd a movable threshold" for the indication on the cathode ray tube screen. Adjus'tm'ent'of this resistor determines the grid value at wh ch tube I80 will conduct, and thus the lowor limit of the indicating thermometers. It is therefore possible, without disturbing the relative heights of the thermometers, to increase or diminish their overall average height.

TIMING CIRCUITS The master pulse oscillator, the stairwave generator, and the synchronizer comprise the timing circuits. A schematic diagram of the timing circuits is shown in Figure 11.

Master pulse oscillator The master pulse oscillator consists of agesfi'lled triode I80 arrangedas a relaxation oscil l'ator'havin'g afrequencyof 1800 per second. The tub e is normally 'non=cond'ucting; The condens er I9I in parallel with tube I80 charges'ir'i' ao== 1 4 cordance' withthetime constant which is the product-of the capacity of the condenser and the sum of thezseries plateresistors I92, I93, ISM-and I95 as modified by the' platecurrent of thetube M8.-

When the voltage across I8'I reaches a critical value, determined'by the grid bias oftube I80,- this tube conducts and discharges the condenser in a few microseconds: During the time that tube I'-is conducting, current flows through its cathode resistance network. When condenser I8i is discharged, tube I is extinguished. The instantaneous high current causes a positive pulse to appear on the tap of resistor I88; this is delivered" through the blocking condenser I98 to the grid'of pentodeiOS-inthe stairwave generator. A positive pulsealsoappearson the tap of resistor I8-I and across resistor I88. These pulses are delivered to the switchin and the output circuits respectively;

The frequency of the master oscillator can be adjusted by varying resistance I88 in its plate circuit. Condenser I89, between the grid network of thyratron I80 and the negative 210-volt source, serves the following purpose: When-voltage is first applied to the master oscillator circuit, both plates of I88 are carried to a potential of -2l0 volts with respect to ground. As I89 charges, current flows from ground through resistors 200 and IN. Until the condenser is fully charged, the grid of tube I80 is thus more than usually negative. This large negative bias has the effect of increasing the breakdown voltage of the tube, and the amplitude of the first few oscillations thereof is increased. These large initial pulses provide an automatic starting of the switching ring in the absence of properly primed gas triodes. As long as any gas triode is ionized by this starting procedure, the self-synchronizing action of the ring circuits previously described will, after one or two cycles of operation, cause the rings to adjust themselves to the proper operating sequence and time phase. The starting action of the first switching rin has been explained in the section describing the switch circuits.

202 is adecoupling condenser which prevents the 18 00-cy cle pulses from passing onto the positive 200-volt-line and to other circuits which draw their power from this common source.

stairwave generator The stairwave generator consists of a pentode 208, a thyratron 204, and a vacuum triode 205 and their associated networks. The stairwave generator serves the following two purposes:

(a) It provides a timing signal which is applied to the horizontal deflecting plates of the cathode-ray os'cillograph.

(b) It supplies a signal to the synohronizer.

The timing signal consists of' thirty equalvdlta'ge increments separated by equal intervals of constant voltage. When applied to the hori- 'zontal deflecting plates of the cathode-ray oscillog'raphthis signal produces a horizontal row of thirty equally spaced spots. The motion of the electron bea'm'trom one position to another occurs in a few-microseconds. The beam is stationary iii each positionfor about Vim second. Aft r'the' completion of thirty steps, the cycle is repeated.

The signal supplie'd'to the synchronizer-has the same-lumbar is opposite in polarity.

The stairwave is produced by charging con-'- denser 2I0 with thirty equal pulses. At the beginning of the cycle, this condenser is uncharged. Pentode 203 is normally biased beyond cut-off. The master pulse oscillator supplies positive point pulses which have constant amplitude and recur at the rate of 1800 per second. These pulses are taken from the tap on resistor I96 and are applied to the grid of tube 203 through the blocking condenser I96. Each pulse causes the same plate current to flow since the trans-conductance of 203 is independent of plate voltage. This, together with the uniformity of the pulses, insures that equal charges pass through the pentode during each conduction period.

Tube 203 is operated between ground and --100 volts. During each conduction period a measured negative charge is deposited on condenser 2I0. The magnitude of the current surges in tube 203 and hence the negative voltage increments across condenser 2I0 are controlled by the resistor I96.

As condenser 2I0 becomes negatively chargi'zl the voltage between the plate and cathode of thyratron 204 increases. This tube is normally prevented from firing by the bias voltage supplied by the resistance network 2 I I, 2I2. After thirty voltage increments have been impressed on the condenser, a positive pulse is delivered to the grid of tube 204 from the slow switching rings, which also act as a counting circuit, as explained in the section describing the switching circuits. This pulse causes 204 to conduct and the charge on condenser 2I0 passes oil therethrough. When the thyratron is extinguished, condenser 2I0 begins to charge again because of the current pulses through pentode 203. This cycle is repeated indefinitely.

If the potentiometer I96 is set too high, condenser 2I0 will become highly charged before thirty steps have been completed. In this case the cathode of thyratron 204 becomes so negative with respect to the plate and grid that the grid loses control, and the tube conducts before the arrival of the timing pulse from the switch ring. This produces an unstable pattern on the cathode-ray screen. If the value of I90 is set too low, the cathode of the thyratron is not sufllciently negative after thirty steps to allow conduction in this tube, in spite of the positive pulse delivered to the grid. In this case, condenser 2I0 continues to charge until thirty more steps have been completed or until the cathode of the thyratron is sufiiciently negative to produce uncontrolled conduction. Various types of multiple and unsatble patterns can be caused in this way. A wide range of adjustment is necessary to allow for differences in the characteristics of different master pulse oscillator thyratrons.

While thyratron 204 is conducting, the cathode potential is determined by the IR drop in the plate lead. Consequently the cathode voltage of this tube at the moment of extinction can be adjusted by varying the resistance 2 I 3.

The voltage appearing across condenser 2I0 is applied directly to the grid of the vacuum triode 205. A positive stalrwave consisting of small voltage increments and a large abrupt decrement is obtained from the plate of this tube and is applied to the horizontal deflecting plate of the cathode-ray oscillograph. A negative stalrwave consisting of small voltage decrements and a large increment is obtained from the tap on potentiometer 2I4. This signal is applied to the avnchronizer.

Synchronizer The synchronizer consists of a thyratron 2I5, arranged as a controlled relaxation oscillator, and a pentode 2I0 which acts as a mixer. The purpose of this circuit is to control the frequency of the master pulse oscillator. It provides a fixed phase relation between the horizontal axis sweep signal on the oscillograph and the power line voltage. To accomplish these ends, the frequency of the master pulse oscillator is adjusted to equal thirty times the instantaneous frequency of the power line.

The relaxation oscillator 2I5 has a free-running-frequency of about fifty-five cycles per second. A 3-volt -cycle sine wave is superimposed on the fixed bias of this tube. Although the average frequency of this signal is usually accurately 60 cycles, the instantaneous frequency may differ from this value. The 3-voit signal on the grid of the thyratron increases the frequency of oscillation of this tube from its free-running value of fifty-five cycles per second to the line frequency. A saw-tooth wave form, caused by the slow charging and rapid discharging of condenser 2 I I, is applied to the screen grid of pentode 2I8. The time constant of this condenser charging through resistor 2I8 is of the same order of magnitude as the period of the line voltage. Consequently the voltage across condenser 2 I 1 increases at a nearly constant rate until thyratron 2I5 breaks down. The voltage to which the condenser charges is determined by the time at which the thyratron begins to conduct.

The negative stalrwave signal obtained from the stalrwave generator is applied to the control grid of the pentode 2I6. The step structure in the wave form of this signal may in this case be neglected. Essentially this voltage increases in a negative sense linearly with time to a fixed value, falls abruptly to zero, then increases again.

. For a given setting of resistances I80 and 2 I3, the

Ill

peak negative voltage of this signal is fixed. The rate at which this peak voltage is attained is determined by the frequency of the master pulse oscillator. Adiustment of potentiometer 2I4 controls the amplitude of this signal.

The negative stalrwave voltage from potentiometer 2I4 returns to zero aboutthree step units (/1800 second) before the positive voltage from thyratron 2|! does. Consequently the two grid voltages effectively combine to produce a current surge in pentode 2I8 near the end of the cycle. This increases the IR drop in the resistance network I82, I83, I84, decreases the plate voltage of tube I80 and consequently decreases the frequency of the pulses from the master pulse oscillator until the positive voltage on the screen grid of pentode 2I0 falls to zero. This pentode does not conduct except for this short interval at the end of each cycle; the length of time during which it conducts is determined by the relative phase of the positive saw-tooth signal on the screen grid and the negative stalrwave signal on the control grid. If the peak of the negative signal and the drop to zero occur too soon, the pentode conducts for a longer period than the normal time of 1m second. This reduces the frequency of thyratron I80 and consequently brir gs the peak of the negative signal into the proper phase with the positive signal. If the peak of the negative signal occurs too late, the length of the pulse delivered by pentode 2I8 through resistors I82, I83, and I84 is decreased and compensation and synchronization are obtained.

1 7 POWER SUPPLY Filter channel power supply The input voltage to the power pack consists of 120-volt 60-cycle alternating current regulated by a constant voltage transformer. The transformer is preferably of large capacity. as 2-kilovolt-amperes. While such capacity is not necessary for the operation of the analyzer alone. it is a convenience in view of the fact that auxiliary equipment will commonly be employed. A fullwave rectifier 228 supplies positive voltage for the system. The rectified voltage is passed through a smoothing filter, comprising inductances 22! and 222, and condensers 223 and 224.

The operation of this circuit is as follows: A decrease in the value of the positive input voltage causes the screen grid of pentode 225 to become less positive. This decreases the plate current through the tube and decreases the IR drop through the resistance 228.

Two beam-pentcde tubes, 221 and 228, are arranged in parallel and the grids of these tubes are tied to the plate of tube 225. Hence. when he plate current of 225 drops, the plate resistance of tubes 22'! and 228 decreases. thus compensating for the original decrease in input volt- "88.

If the voltage on the screen grid of amplifier 225 were controlled by the resistances 228 and 230 alone. the variations of plate resistance of tubes 22! and 228 would overcompensate the input voltage variations. To eliminate this eilect, the screen grid of the amplifier is connected to the cathodes of 221 and 228, through resistance 23!. 23! is tied to the resistance network 229. 230 at a point having the same voltage as these cathodes. Thus. there is no D. C. voltage drop across resistance 23!.

The excess signal voltage on the cathodes of 221, 222, caused by overcompensation tends to increase the voltage oi the screen grid of the pentode 225 because of signal current through resistances 238 and 23!. This adjusts for the overcompensation. The value of 23! is chosen to obtain exact compensation.

Sudden variations in the output load operate in a similar manner on the control grid of 225 through condenser 232. If the load is momentarily increased. a negative pulse is delivered to the control grid. This decreases the plate current the pentode and decreases the grid bias voltage of the regulator tubes 221. 228, thus decreasing the plate resistance oi the latter. Condenser 232 also prevents high irequency tube noise from the amplifier tube 225 or the voltage regulating tube 235 from appearing in the output. The nominal output potential of the regulator depends upon the grid bias of the pentode 225. and this is controlled by resistor 233.

Tube 238 has a characteristic such that the voltage drop across it is nearly independent of the current through it. This fixes the voltage of the cathode of pentode 225. In the circuit described and shown it is fixed at m volts above ground. Resistance 23'! insures sufilcient current through regulator 235 to maintain that tube on the stable portion oi its operating characteristic.

The negative voltage for grid-bias supply is obtained from a full wave rectifier 238. Two voltage-regulating tubes 238 and 240 insure the stability of this voltage supply. Two leads, each at l50 volts, are used to supply the output network in each filter channel.

Three additional electronic voltage regulators, identified in their entireties as 24!, 242, and 243, and identical in operation with the regulator above described, are connected in parallel with the first mentioned regulator. The one voltage regulator tube 235 serves all of these circuits.

Main power supply The main power supply furnishe operating power for all units 'of the assembly with the exception of the filter channels and the cathoderay oscillograph. It contains two full wav rectifiers, 250 and 25!. one half-wave rectifier, 252, and three electronic voltage regulators. A positive 200-vo1t line is regulated by a circuit which includes tubes 253 and 254 and which functions in the same manner as the electronic regulator in the filter power supply. The bias on the screen grid of amplifier 253 is fixed by the resistance network 255, 255. and 251. And the resistance 258, in order to satisfy the condition that no direct current flow therethrough, is tied between resistors 255 and 258 at a point such that its potential is equal to the average potential of the cathode of tube 254. Resistor 258 is adjustable in order that the proper degree of compensation may be obtained.

A second electronic regulator, including tubes 288 and 28!, supplies the positive 110-volt line. The cathode of the amplifier tube, 26! in this case, is grounded directly. Voltage regulator tubes 252 and 253 are provided, and these operate (for the apparatus described) between ground and 210 volts. Between these tubes. at a point of volts potential, a lead is taken, and this lead supplies the reference voltage for the electronic regulator, and, by means of the resistance networks 284, 255, 288, and 281. 268, 289, the grid biases for the tubes.

A third electronic regulator, identical with. the one Just described. comprises tubes 210 and 21! and associated elements: this supplies a negative IOO-voit source. The reference voltage for this current is -210 volts. and is obtained from the negative side of the voltage regulator tube 263.

These two circuits are the same as thosealready described except for minor differences occasioned by the diiferent positions of the voltage regulator tubes in the circuits. The current through these tubes is obtained from the halfwave rectifier 252. Tubes 282 and 258 stabilize the negative side of this half-wave rectifier at -2l0 volts. The load variations on this grid supply line are not sumclent to require the use of an electronic voltage regulation.

The 3-volt A. 0. signal used in the timing circuits is taken between one side of the 6.3-volt filament lead and ground.

VOLTAGE REGULATORS patent application 8. N. 869,556, filed May 14,

Like the regulator of Figure 12, .thatoiFlgure licomprisesa voltage dividing network, consists. ing,oi resistors 210; 21!; 212, and 213, across the. supply lines, and an amplifying pentode 214, the screen grid of which is varied in accordance with changes in input potential. A rise lnscreengrid. P tential, due to anlncrease in input,.inc. eas os the current through the tube, and thereby,.en.-.- large-s. the potential drop across its plate-load, resistor 215. grid" potential of the series regulator tube-21.8,, increasing, the plate resistance. This operation. controls the output potential of the regulator for changes in input potential.

Compensation oI,-output potential, for; shorttime and long time. variations in effective-loadresistance also is providedior in novel-manner. Asexplained in connectionwith the regulator oi Figure 12, any short-time variationinload cur.- rent is impressedon the control-grid of amplifier. 21 l=through the network including resistors: 211, 218, 219.and.condenser 280-. 21%serves to deter.- minethe nominal output of the regulator. Short time. changes in load current cause potential changes which are coupled to the control grid of pentode 214. through condenser 28!] and which are.then compensated for as already'described.

Any change in load, current continuing fog-a p eriodlonger than that for which condenser 280- canmaintain the change at the grid of the applinet, 214 will develop,achange in potential-across resistor 28I,.through which the pIateFcurrent 02' the tube 214 and all load. current passes. A; change oi; this potential drop-varies the cathodeto-controlgrid potential of tube 2141a theyproper; phase to oppose any change in the output poten-- tialofthe regulator.

The magnitude ofthe potential drop across 28!- is determined by adjustment of the resistance. andthe value of resistance 28!- at which neither overcompensation nor undercompensation will occur. with changes in load current may be readily ascertained.v

A-gas-fllled regulator tube 282 is used to raise the potential of the cathode of amplifier 214 with respect to ground: potential.- Since fluctuations oi" the-operating pot wtial of 282' will vary the grid-cathode potential oiythe regulatorampliflor: andthereiore theoutput oi! the system, these-- lection of the tube,282rshould take into account the ability of the tube to maintain its own operate ing potential. It. has been iound that a type VR-105/30 tube is. tobe preferred toa typo-l CD-2005 in this connection. A battery may be substituted for the gas-filled tube, and willcliminate short-time fluctuations, but may introduceslow. changes in-the output due to thezcharging. eiiect oi the cathode. current oi the pentode 214..

In determining the point of connection or the screen grid pentode 214 to the voltage dividing network 210, 21l,.212, 218, it:is necessary, in. addition to obtaining the proper operating potential for the screen grid, to allow enough of the input fluctuation to appear on the screen grid that the regulator actually ovorcompensates therefor, below the resistance 2" is inserted in the circuit. A iall in input potential will, in other words, produce a slight rise in output potential.

Alter DIODOrtiOnlng the resistance network so. that the screen grid overcompensates for input. variations, all traces of overcompensation are ro-- moved by the insertion and proper adjustment 0!. the variable resistance 28!. Resistance 2 must not carry any load current, and, to this and,

and 285 are at the sameravemge-pot n l ly voltage changes will then appear across resistor 283. This. resistc.,-,in series with theload reslstance, and,with point 2B5 maintained. atroutnut. potential, forms a shunt for screen-signal. potential across thelower portion of the voltage divider. network. comprising resistors 21 i, 212-.and; 213 in series. By adjustment of 283, the voltage..- change appearing at point 284, and therefore on This action add to thenegative 1d. the screen gridmf pentode 21l;.mav::he attenuated. It is clear, then, that for som particular value ot resistance 28!; there will be; nochan e in output dueto changes in input: Byproper adjustment ofthiswarlable resistance,- therefore; changes in the plateresistance-oi tube 216- are' caused to-oompensate' exactly for changes in inputvoltage.

Forsome applications or the voltage-regulator,- compensation for long-time voltage variations 20.. may beofno importance. Insuch cases; variableresistor-28l'may be omitted; as in Figures Hand 13, and the regulator-will then compensate,- oniy for supply potential variations and short time load-variations. It will still maintain the output reasonably constantior-long-time variations; but

the output can be-expectedto vary slightly-with-. long-time-load changes, of-- the order of twenty; per cent. capacity'flil'and resistor 284 should be retained, not only to provide-shorhtime-load compensation but to eliminate the fluctuations produced by the; regulator tube 282-, as 'already' described:

he ormal" operat nz; urrent ;of' the screen and ofpentode- 21- is: drawn from the input through the voltage-divider networkofresistances 210, 21l, 212 and 213 in series. Any input variationwill cause a changein the screen-grid. current which will produce a. potential; drop across 210 and 21',i'in'series tending to oppose the; regulatingaction 01' the change in screen-grid potential. It'is advisable; therei'ore', to keep the current in this bleeder. network ashigh as possible, so that'the degenerative eflectoi the change. in screen current will;-remain at;a minimum. With" atwo milliampere current; the regulator.

retains control over the circuit at fullilcad .with

input variation ,oi' plus-or-minus ,forty, percent; with a one,mi1liampere current; lllusror-minus. twentypencent.

In Figure. 16: is sho n a. modiiledwoltage regu: lator adapted for. higher. output .pgt ntials, than t eresulstors. demibedg, esltbenutuutnotential; is increased, it becomes moraimmitanttMtthe. electrodes oithe regulator amplifier, ztltlmfi'isure. 15. e. operatedaanearly as,possib1eto tlie, hl tn t tial; And it isthennecessarvm0n-- erly,to couple to,thecontrollelectrodesinnutandl output potential changes. The cathodeori'the. ampliiiermar be. operatedats. higher. pptentialf from ground by.using .two..tubesinseriesinnlwa oiiths single voitagerregulatortuhezsl. Thiswill, however, increase the .difllculties growing out. of the smaihshortetima fluctuationacharacteri'stic oi s s-fllledyoitaga-regulatontube e A.more.. desirable methoiisillustratediinmgurelfi Tharegulator-amplifler. cathodertoesuppressor. con.- nection shown in Figure. 14 lsslimiuated. andthe. suppressor grid oaths. tubelis connected to.the voltage-divider, network; 183,. 28A 285,.,as.ali 2". This connection-allows the suppressor. grid. to. exert someroguiating aotiomiacouiunction. with the screen .grid when.ths attenuation .ratio...

it is positioned in the circuit so that points 2, 75. becomes so groat-i-duostdthanecessity rancher ati'ng' the screen grid at its proper potential with respect to the cathode at high output valuesthat the amplification of the screen grid alone is not sufficiently high to control the plate current of the tube for proper regulation. The resistance network should be so designed that the potential at point 295 is essentially the same as that of the cathode of the amplifier 290.

OPERATION The analyzer is designed to operate on 120-v0lt 60-cycle regulated power. It draws about 9 amperes at this voltage. The power factor of the analyzer is about 0.99.

Power is distributed to the various elements of the invention in accordance with the diagrammatic circuit drawings herein through any convenient arrangement of junction boxes; and connection is made to an oscillograph.

The voltage level of the input to the analyzer should be of the order of 0.1 to 1.0 volt. An attenuator or voltage divider should be provided in order to maintain the input signal voltage at this level.

The voltage supplies should be carefully adjusted to their proper values. Some convenient meters, as 300, 311i, 302 and 303 (Figure 13) should be provided for this purpose. The meters illustrated indicate respectively the A. C. line voltage, 120-volts, the positive ZOO-volt plate supphr, the positive 110-volt plate supply, and the negative l-volt grid bias supply. The positive ZOO-volt, positive 1l0-volt and negative l00-volt supplies can be controlled and adjusted by the variable resistors 304, 268 and 305, respectively.

Six adjustments are provided for use in securing the proper pattern on the oscillograph screen. These may be conveniently termed Zero, Gain, Synchronizer, Phase, Frequency and Stabilizer; and they correspond respectively to the variable or adjustable resistors I80 and I81 (Figure and 2, 213, I93 and I96 (Figure 11). Y

The following procedure is suggested'for setting up the pattern: all pattern controls are set at minimum. except the Zero control which is at maximum. The intensity and focus of the.

oscillograph are fixed at convenient levels; the frequency" switch of this instrument is turned off; the Y-axis amplifier is at zero, and the X- axis amplifier is at 30.

With the power turned on, the X and Y positior. controls of the oscillograph are adjusted until 3. spot appears on the screen. This spot will repeatedly move horizontally across the screen. Adjustment of the Stabilizer. control will produce a pattern of thirty spots in a horizontal line. Increase Gainuntii vertical lines appear, one above each of the thirtyspots, to a convenient height, from one to three inches.

Preferably the Stabilizer setting is decreased until the pattern becomes unstable; and stability is reobtained by adjustment of the Synchronizer. This procedure is desirable, because otherwise the pattern may become stable with the line or thermometer" at position 1 displaced from its proper position.

Adjust Frequency if any ripple appears in the pattern; and adjust Phase for maximum stability.

Decrease Zero until the right and left hand thermometers are justvisible above the horizontal axis. The intermediate thermometers will in general have irregular heights. All controls except Gain are now correctly set. Minor adjustment of Frequency may be necessary Occasionally f the pattern develops aripple, i. e., a slight, recurrent shifting of the entire pattern across the screen of the oscillograph. which may be caused by spurious magnetic deflection of the electron beam when the frequency of the electronic switch differs slightly from that of the power-supply line.

Two controls for each filter channel are pro vided. These may be conveniently termed Balance and Gain Zero, and they are respectively the resistors 51 and 54 of the filter circuits (see Figure 3).

Increase Gain until the right and left hand thermometers are about 2% inches high. With no signal on the analyzer input, adjust the twenty-eight Balance adjustments, in order of increasing frequency, until the twenty-eight intermediate thermometers have equal heights.

The level of the two end thermometers is the zero signal level. While this adjustment is being made, all of the individual Gain Zero controls should be at zero. It should be noted that this adjustment is made at a high Gain setting. As a consequence a certain amount of fluctuation may occur in the height of the thermometers. This fluctuation may, in general, be disregarded. It should also be noted that the heights of the individual thermometers will vary slowly with time as the instrument warms up. To minimize this and similar effects, it is suggested that the analyzer be turned on at least an hour before accurate settngs or measurements are made. After this adjustment has been made, return Gain to a standard setting.

Arrange a beat-frequency oscillator on the input of the analyzer in such a way that a signal of constant voltage and adjustable frequency can be applied to the instrument; the use of a vacuum-tube voltmeter across the input of the analyzer is suggested. Set the oscillator frequency at about 25 cycles. Adjust the oscillator voltage as read on the vacuum-tube voltmeter to 0.1 volt or some other convenient value. Adjust the lowpass Gain Zero control until the low-pass thermometer rises to 2 inches. Adjust the frequency of the oscillator to obtain the maximum deflection of the thermometer. Reset the oscillator voltage if necessary and readjust the low-pass Gain Zero control to obtain standard deflection of approximately 2% inches.

The same general procedure should be followed for each of the tuned channels; namely, set the oscillator for the lower frequency of maximum response for the channel, adjust the oscillator voltage to the standard value (0.1 volt, R. M. S.) and. adjust the- Gain Zero control for the channel in question to obtain standard deflection of the corresponding thermometer. It should be noted that there is a small drop in response at the center of the frequency-response curve of each filter channel. The lower frequency of maximum response for each filter channel should be used for this adjustment.

The all-pass channel Gain Zero control should be adjusted in the same way except that a, larger input voltage (0.2 or 0.4 volt) should be used in order to provide a condensed scale for the allpass thermometer. The displacement of the allpass thermometer is proportional to the sum of the displacements of the other thermometers.

In adjusting the Gain Zero controls, care 

